M A S T E R ' S T H E S I S
Digital Broadcasts Using a FM Transmitter
Robert Selberg
Luleå University of Technology MSc Programmes in Engineering Computer Science and Engineering
Department of Computer Science and Electrical Engineering Division of Signal Processing
2006:269 CIV - ISSN: 1402-1617 - ISRN: LTU-EX--06/269--SE
Robert Selberg
June 2006
Every night, scrambled audio newspapers are broadcasted over the terres-
trial FM network all over Sweden. To be able to listen to these papers,
the listener have to borrow a special receiver from Taltidningsnämnden, a
Swedish government authority.
Rubico ABand Microbit2.0AB have developed anew receiver called
Adelausingdigitalcomponentsandtheyhavewishtoalsomakethebroad-
castsdigital. It is thepurposeof this thesisto investigate suitable modula-
tion, symbolsynchronization, symboldetection and equalization techniques
for digital transmissions over the existing FM network and implement a
proof-of-concept decodersystemableto run onthe Adelareceiver.
Oftheinvestigatedmodulationtechniquespulseamplitudemodulation,
quadrature amplitude modulation and Gaussian minimum shift keying
pulse amplitude modulation (PAM) was implemented and tested in a lab
environment.
The result was that pulse amplitude modulation is not an appropriate
modulation for high speed data broadcasts. It is sucient for 23 kBaud
2-PAM broadcasts(in mono)but ifhigher speedis required,a carriermod-
ulation like quadrature amplitude modulation is preferable. However, the
resource requirement of the implementation was found to be very low. In
theory,the presentedsystemcanbe implemented ona DSP systemcapable
ofaslowas5-10MIPSand2KBRAM,whenonlycalculatingtheexecution
timeandmemoryneededbythelteringoperationandusingtheparameters
oftheimplementation presentedinthis thesis.
This master's thesis is the nal work for my Master of Science degree in
computer science/signalprocessing at LuleåUniversity of Technology. The
work hasbeen performedat RubicoABduring thewinterand spring 2005-
2006.
Rubico AB hasdeveloped a digital receiver for radio broadcasted audio
newspapers,calledAdela,whichis compatiblewiththeoldreceiversusedin
Sweden. However, the old receivers tend to break too often and therefore
they are to be replaced with Adela, one after another. In time, all analog
receiverswill bereplacedandtherewillbenoneed foranalogbroadcasts. It
isthepurposeofthisthesistoinvestigatesuitablemodulation techniquesfor
digital broadcast over the existing FM network and make proof-of-concept
implementation ableto run on the Adela hardware.
IwouldliketothankmyexaminerDr. FrankSjöbergandmysupervisor
at Rubico AB, PerJohansson, for their invaluable supportthroughout this
thesis. Iwouldalsoliketo thankCamillaIsakssonandNilsCarlsonfortheir
proofreading and mycolleges at Rubico; HansEklund, AndersLarsson and
Mika Kallijärvifor their viewpoints andcompanyunderthese months.
RobertSelberg
Luleå, Sweden
June 2006
1 Introduction 7
1.1 Background . . . 7
1.2 TheCurrent Receiver . . . 8
1.3 Advantages withDigital Broadcasts. . . 8
1.4 ProjectGoal . . . 9
1.5 ProjectLimitations . . . 9
1.6 Method . . . 10
1.7 Outline ofthe Thesis . . . 10
2 Modulation 11 2.1 Basics . . . 11
2.2 PulseModulationTechniques . . . 12
2.2.1 PulseAmplitude Modulation . . . 14
2.2.2 Quadrature AmplitudeModulation . . . 16
2.3 Pulses,Eye Diagramsand Matched Filters . . . 18
2.3.1 PulseProperties . . . 18
2.3.2 Eye Diagrams . . . 21
2.3.3 Matched Filters . . . 21
2.4 Gaussian Minimum ShiftKeying . . . 23
2.5 SpectrumAnalysis . . . 24
2.6 Discussionand Conclusion . . . 25
2.6.1 Reasons forUsing PAM . . . 26
2.6.2 Reasons forUsing QAM . . . 26
2.6.3 Reasons forUsing GMSK . . . 26
2.6.4 Conclusion . . . 26
3 Demodulation 29 3.1 SymbolSynchronization . . . 29
3.2 SymbolDetection . . . 32
3.3 Adaptive Equalization . . . 33
4.2 MATLABImplementation . . . 38
4.3 Real-TimeImplementation inC . . . 39
5 Results 45
5.1 Investigated Modulations . . . 45
5.2 Implementation . . . 46
6 Discussion and Conclusions 49
6.1 Discussion . . . 49
6.2 Conclusions . . . 50
6.3 FutureWork . . . 50
Introduction
Everynight,localnewspapersarebroadcastedonSverigesRadioP1allover
Sweden. Thesenewspapers arefor thevisually impaired, afatics, dyslectics
anddisabledpersonsthatfor somereasoncan notreadprintednewspapers.
The receivers usedfor recordingthese newspapersarenowoldand have
to be replaced by new ones. The new receiver is built upon a digital sig-
nal processor but the broadcasts still remain analog and it is the purpose
of this thesis to investigate suitable techniques to send and receive digital
broadcasts. Finally a complete systemwill be built to evaluate thechosen
techniques.
1.1 Background
Taltidningsnämnden, aSwedish government authority,isresponsibleforthe
publication of newspapers in spoken form. They also distribute funds to
the66 1
papers thatreadintheir news and oerthem asaudionewspapers.
Toprevent eavesdropping, thebroadcastednewspapersarescrambledbefore
transmission and therefore a special receiver has to be used to be able to
listentothenewspapers. Formoreinformationaboutthecurrentscrambling
technique, seeLarsson[13 ].
The newspapers today,are recorded on a compact audiocassette by an
old analog receiver that can only descramble and record the newspapers;
it is not able to replay them. This receiver, which was developed about
20 years ago, is out of date and tends to break down too often because of
the mechanical parts that get worn out with time. It is also expensive to
repair since itishard toget spareparts. Taltidningsnämnden hastherefore
givenRubico ABand Microbit2.0AB acontract to develop anew, digital,
receiver called Adela 2
. This receiver was put in test operation during the
1
AccordingtoTaltidningsnämnden[18 ].
2
Adelaisalsothenameofthewomanwhowasinvolvedinthebeginningandtherst
rstquarter2006. For morenon-technical information about Adela, seethe
Adela website[19].
The Adela receiver usesthe same descrambling technique as theold re-
ceiver,butthe decodingismadeusingadigitalsignalprocessor (DSP).The
reasonfor thisisthattheoldreceiversarereplacedgradually andthebroad-
castsmustbedecodable byboth receivers. However, therearealso plansto
digitize the radiotransmissions and it isthepurposeof this thesisto inves-
tigate and determine a suitable modulation technique to be usedinside the
existingFMsystem.
1.2 The Current Receiver
Today's analog receiver has some severe limitations; it can only record one
paper per night and each paper lls one 90 minutes cassette. This means
thatapersoncan onlysubscribetoonepaperatatimeandifheorshegoes
onajourney,e.g. overaweekend,someonehastochange thecassetteevery
day. Ifnot,theolderpaperswillbeoverwritten. Besidethis,theoldreceiver
isbig, heavy and the soundquality is very dependent on thequalityof the
analogcassette.
The new digital receiver does not have the same limitations as the old
one. The biggest benet for Taltidningsnämnden is that Adela does not
have any moving mechanical parts that getworn out and therefore it does
not need to be repaired often. From a user's point of view, the biggest
benets arethepossibilitytosavefour newspaperson thememory card 3
,it
iseasyto change article,thereceiverissmallanditcanbebattery-powered.
Otheradvantagesareplaybackspeedcontrol,i.e. youcanplaybackanarticle
faster or slower atyour desiredspeed,which isan requested feature andan
recorded help-voice thatgivestheuserfeedback.
Formoretechnicalinformationabouthowthenewdigitalreceiverworks,
seeLarsson[13 ] andPääjärvi[15]
1.3 Advantages with Digital Broadcasts
There aremany benets of digital broadcasts,the increase inaudioquality
is probably the chief benet from a user's point of view. However, there
areother more concealed benets like higher spectraleciency 4
, simplied
rmware updates and enhanced security through encrypted transmissions.
Mostpeoplewillnot thinkaboutthermwareupdatesorthebroader range
of available newspapers, but these features will greatly reduce thesoftware
maintenance costs and bandwidth usage associated with more transmitted
3
Dependingonthesizeofthememorycard.
4
newspapers and in the long term, it will hopefully lower the costs for the
customers.
Thepossibilityofoeringnewservicesisaninteresting featurewithdig-
ital broadcasts. The libraries, for example, canhave a servicewhere people
can borrow their audio books without having to visit the actual library.
When the loan has expired, the audio book will simply be deleted by the
receiver; no physical audiobookhasto be returned.
However,digitalbroadcastdohavesome drawbacks. For example,ifthe
receiver conditions deteriorate, like in a snow storm, the data stream may
collapse and the data is lost. This may be a problem for some users, but
typicallyit isnot abig problem. The benets far outweighthedrawbacks.
1.4 Project Goal
The goal of this thesis has been to investigate and evaluate suitable mod-
ulation techniques for use in data transmissions over a FM channel. It is
preferred to nd a modulation that makes it possible to send compressed
audio, i.e. transmit more than 64kbit/s,but not arequirement.
Whenan appropriatetechnique hasbeenchosen; itwillbeimplemented
inan embedded system, using theAnalog Devices BlacknBF532 DSP,to
demodulate a datastream inreal-time. The goalis to make theimplemen-
tationrun onasystemwithaDSPcapable of200MIPS 5
and 32KBRAM.
To build the decoder part of a communication system; a synchronizer,
detectorandpossiblyanequalizerhasto beused. Thereforethese partswill
also be investigated andsuitable algorithms willbeimplemented.
TheconclusionsdrawnfromthisprojectdoesnotonlyapplytotheAdela
digital newspaperreceiverbut also to other applications which want to use
theexistingFMradio network infrastructurefor databroadcasts.
1.5 Project Limitations
The tests performed have mostly been done in Mathworks MATLAB [7].
No real-world tests have been done, due to practical reasons but the nal
implementationhasbeentested inalabenvironmentusingaFMmodulator
andtheAdelareceiver. Thiswastosimulateareal-worldtest. Unfortunately
theeectsofmulti-path propagationand otherinterfering signalscouldnot
be investigated using thelabequipment.
The MATLABtestsperformedon themodulationsareresistance toad-
ditive white Gaussian noise (AWGN) and timing errors. No timehas been
giventondingtheoptimalparametersofthedierentpartsinthecomplete
system.
5
1.6 Method
In the beginning of this project, a literature study of dierent modulation
techniqueswasdone 6
. Afew ofthe investigated techniqueswasselected for
acloserlookaccordingto the following criteria:
•
Well tested technique used inreal applications.•
Suitable for transmissionvia aFMtransmitter.•
Feasible to investigate and implement within the time frame of this thesis.After the selection was performed, the three selected modulations was
implemented and tested inMATLAB. The testsresulted inthat one mod-
ulationwasselected for real-time implementation; but to be ableto decode
the signal, appropriate symbol synchronization, equalization and detection
techniqueshasto bechosen. Thereforeanother literaturestudy was done.
After the second study, the selected techniques were also implemented
and tested in MATLAB. Thereafter a complete receiver system was built
andtested,inMATLAB,onamodulateddatasignal;whichwastransmitted
throughtheFMmodulator and recorded byAdela.
When theMATLAB implementation was working, itwas rewrittenina
formthatcould be,and was, implementedinreal-time.
1.7 Outline of the Thesis
Asthereader may have noticed,the rst chapter is an introduction to this
master's thesis. The second chapter will introduce the basic concepts of
digitaltransmissions;theoryaboutpulseshapes,eyediagramsandaderiva-
tionofmatched ltersarediscussed. Apartfromthis,thethree modulation
techniques investigated PAM, QAM and GMSK are explained and an
account ofwhy the chosen technique waschosenis given.
Chapterthreeisaboutdemodulation ofthereceivedsignal. Inthischap-
ter, the importance of the symbol synchronization, symbol detection and
adaptive equalization are explained. A derivation of how to make an opti-
malmeansquareequalizerandplots ofhowitimproves thesignalisshown.
Chapter four explains theimplementation indepth, some implemented
andunimplemented optimizationsarealso explained.
Chapterveandsixsummarizestheworkbydiscussingtheresults,con-
clusions,problems andfutureimprovements.
6
The tested modulations are: Pulse Amplitude Modulation (PAM), Quadrature Am-
plitudeModulation (QAM), Quadrature Phase ShiftKeying (QPSK), Oset Quadrature
Phase Shift Keying (OQPSK), Minimum Shift Keying (MSK)and Gaussian Minimum
Modulation
Have you ever wondered how digital data is transmitted through a wired,
beropticor wirelesschannel 1
? Ifyouhave,thischapterwillhopefullygive
you,asareader,some understandingofhowdigitalcommunicationsystems
work.
This chapter will introduce the basic concepts of modulation. First a
short introduction of how a communication system works is given; then
two pulse amplitude modulations are discussed, one baseband modulation
calledPulseAmplitudeModulation (PAM)andonecarriermodulationcalled
Quadrature Amplitude Modulation (QAM). After that, theory about pulse
shapes,eyediagramsandmatchedltersispresentedtogetherwiththeGaus-
sianMinimumShiftKeying (GMSK)modulation,whichisusedintheGSM
cellphone system. Finally a short spectrum analysis of the FM system is
doneandamotivation ofthechoiceofmodulationto be usedinthis project
isgiven.
2.1 Basics
So whyis the datamodulated beforeit istransmitted? To make thetrans-
mittedsignaltwithina certainbandwidthlimit,make itresistanttonoise
andeasy to decode.
Figure 2.1 shows a simple model of a communication system where the
data enters the system from the left, becomes modulated and transmitted
by the transmitter. After transmission, the signal will travel through the
channel and get distorted by both the channel and noise at the receiver.
The receiver therefore applies a so called matched lter, to remove noise,
andanequalizer,tocompensate forthechanneldistortions,beforesampling
anddecoding.
1
Thecommunicationchannelisaphysicalmediumthatisusedtosendthesignalfrom
Figure2.1: Simplied system model without a symbol synchronizer for a digital
communicationsystem. Ifananaloglterisused,itisimplementedbefore
thesampler.
Figure2.2: Exampleofanonreturntozero (NRZ)pulseandapossiblepulsetrain.
2.2 Pulse Modulation Techniques
There areseveral ways to modulate digital data. Oneof the simplestbase-
band modulations is non return to zero (NRZ)[17], which is a special case
ofPAM.TheNRZmodulationmapsthedigitalbits0and1tothealphabet
[-1,+1], which in its turn is used together with the NRZ square pulse to
create the necessary transmission symbols. The pulse used by NRZ and a
possible pulse trainareshown inFigure2.2.
The transmission symbols, called symbols from here on, are the basic
buildingblocksofasignalandthesmallestunitsacommunicationsystemcan
transmit. Theycontains the information ofone or morebits, dependingon
thesize ofthealphabet. Thenumberofbitsasymbolcontainsiscalculated
accordingto the following formula:
nr bits =
log2 (alphabet size).
(2.1)The NRZ modulation is easy to synchronize due to the sharp edges of
thepulse,but theyalso makesthepulsetrain verybandwidthinecient. A
pulse train with independent symbols has the same frequency spectra asa
singlepulse and the discontinuities in theNRZ pulse makes it wide spread
inthe frequency domain,asshown inFigure2.3(c). Onewayto reduce the
bandwidthisto round othe cornersof thepulse,but thenitisnot aNRZ
pulseanymore.
Assaid,NRZis aspecialcaseof PAM. Itserveswell asanintroductory
exampleofamodulation,butitisbettertodiscussthegeneralcaseindepth.
Thereforethe followingsectionwill discussPAMand insection 2.2.2,QAM
isdiscussed.
−6Ts −4Ts −2Ts 0 2Ts 4Ts 6Ts 0
0.5 1
Time (s)
× 1/ √ Ts
−3/Ts −2/Ts −1/Ts 0 1/Ts 2/Ts 3/Ts 0
0.5 1
Frequency (Hz)
×√ Ts (a)
−6Ts −4Ts −2Ts 0 2Ts 4Ts 6Ts 0
0.5 1
Time (s)
←α =30%
× 1/ √ Ts
α =100%
↓
× 1/ √ Ts
−3/Ts −2/Ts −1/Ts 0 1/Ts 2/Ts 3/Ts 0
0.5 1
Frequency (Hz)
←α =30%
×√ Ts (b)
←α =100%
×√ Ts (c)
−6Ts −4Ts −2Ts 0 2Ts 4Ts 6Ts 0
0.5 1
Time (s)
× 1/ √ Ts
−3/Ts −2/Ts −1/Ts 0 1/Ts 2/Ts 3/Ts 0
0.5 1
Frequency (Hz)
×√ Ts (c)
Figure2.3: Some pulseforms and their Fourier transforms: (a)sinc, (b)raised-cosine
and(c)NRZ.Thepulsesarescaledtomaintainunitenergyas
T s
changes.−4Ts −2Ts 0 2Ts 4Ts 6Ts 8Ts 10Ts 12Ts
−1.5
−1
−0.5 0 0.5 1 1.5 2 2.5
time (s)
Figure2.4: 2-PAMpulsetrainbuiltfromasincpulseusingthebits[0101101011] .
Thedottedlinesaretheindividual pulses. Theblackline isthesumofall
dottedlines.
of spectral ecient pulses are examined in detail. The sinc, raised-cosine
(rc)and root raised-cosine (rrc) pulses.
2.2.1 Pulse Amplitude Modulation
Pulse amplitude modulation (PAM) [16] is one of thesimplest modulation
techniques available, it can be used to modulate the signal by itself or as
apart of some more complex modulation like QAMand GMSK. Thepulse
train inFigure 2.2is infactaPAM signalmodulated withtheNRZ square
pulseshownto theleftofthetrain. AnotherexampleofaPAMsignalisthe
pulsetrain inFigure2.4.
Buthowdoyoubuildapulsetrain? Firstwehavetochooseapulse
v(t)
,andsome databits to modulate. Letschoosethesincpulse ofFigure2.3(a)
andthedatabits[01 011 01011]. Themathematicalexpressions forthe
sincpulse inthe timeand frequencydomain are:
sinc
(t) = sin(πt/T s ) πt/T s
(2.2)
and
sinc
(f ) =
1, |f| ≤ 1/2T s
0, |f| > 1/2T s ,
(2.3)respectively, where
T s
isthe symbol time, i.e. thetimebetween two pulsesA
S 1
S 2
Figure2.5: IllustratingA,whichishalfthedistancebetweentwoneighboringsymbols.
orthetimebetween thetopofthesinctotherstzerocrossingofthex-axis,
seeFigure 2.3(a).
Then we have to build the actual pulse train
s(t)
,by mapping thedatabits to symbols,e.g.
a n = ±1
,and summing the symbols multipliedwith atimeshiftedversionof the pulse
v(t)
:s(t) =
N
X
n=0
a n v(t − nT s ).
(2.4)Theresultingmodulated signal,showninFigure2.4,isnowreadyfortrans-
missionthrougha basebandchannel.
Othersymbolsthan
±1
canbeused. Infactallrealnumberscanbeusedastransmissionsymbols,but itiscustomto take one bitora clusterofbits
andusetheintegers
±1, ±3, ..., ±M − 1
multipliedwithAassymbols,whereM
istheorderofPAM2andA
,ascalefactor,ishalfthedistancebetweentwoneighboring symbols inthe constellation 3
, see Figure 2.5. When specifying
anorder ofPAM,itis common to writeit intheform: M-PAM.
Thechoiceofsymbolconstellation aectsthe energy neededtotransmit
the signal, therefore the shape has to be chosen wisely. The mean symbol
energy
E av
for a random datasignalof orderM
is calculatedbytakingthemeansquareof all pointsin thesymbolconstellation:
E av = A 2 M
M
X
m=1
(2m − 1 − M) 2 = A 2 M 2 − 1
3 .
(2.5)The symbol transfer rate in a communication system is limited by the
symbol time
T s
, which is limited by how much intersymbol interference 4(ISI) thesystemcancope with. Ifno ISIisdesiredat theoptimalsampling
2
TheorderofPAMisthenumberofbitsinthecluster.
3
Agroupoftransmissionsymbolsiscalled asymbolconstellation.
4
Intersymbolinterferenceisthe nameofa problemcausedby symbolsthat areover-
points, thenthe maximum symboltransfer rate dependson the bandwidth
ofthe channelaccording tothe following expression:
T s = 1
2BW ,
(2.6)which can be derived from eq. (2.3) if the pulse maximizes the channel
bandwidth.
This makes it possible to send
2BW
symbols/second (Baud) through a channel witha bandwidth ofBW
Hz. However, it is not always you wantto maximize the throughput this way since if there is unused bandwidth
available,itcanbeutilizedbytherrc-pulse tocreateapulsethatiseasierto
implementandtosynchronize. Therrc-pulseanditspropertiesarediscussed
insection2.3.1.
After the data is modulated and transmitted it will travel through a
channel to the receiver, but before it reaches the receiver, the channel will
distort the transmitted signal and noise will be added, see Figure 2.1. To
decode the signal to a data stream, the received signal must rst be sam-
pled and ltered by a matched lter, this is done to remove asmuch noise
aspossible 5
. Thereafter, a symbol synchronizer is used to synchronize the
samplerwiththesignalsothenextsamplewillalsobecorrectlysampled
anda detectoris usedto mapthesamples into symbols,which aredecoded
into binary digits, i.e. the output data. This can be an easy or hard task,
depending on how the channel aects the signal. If the channel is of the
multi-path type, i.e. the transmitted signalarrivesat thereceivervia mul-
tiple propagation paths, an equalizer must be used to compensate for the
channel distortions. If the channel ltering is changing, then the equalizer
must adapt to the changes, otherwise the performance of the detector de-
creases. Adaptiveequalizationusingtheleastmean square (LMS)algorithm
isdiscussed inchapter 3.
2.2.2 Quadrature Amplitude Modulation
Quadrature amplitude modulation (QAM) [16] is frequently used indier-
entcarriertransmissionsystemsfromtheoldestmodemtothenewestADSL
modems and wireless network cards. It is a more sophisticated amplitude
modulationtechnique that uses two PAM pulse trains to modulate two or-
thogonal carriers,
cos 2πf c t
andsin 2πf c t
, that are added together beforetransmission. The most elegant way to describe the modulation is with
complexnotation:
s(t) = Re
e −2 iπf c t ·
N
X
n=0
a n v(t − nT s )
,
(2.7)5
This descriptionis fora systemwithandigital matchedlter. Ifananalog lteris
(a) (b)
Figure2.6: Twoexamplesof16-QAMsymbolconstellations,onequadratic(a)andone
non-quadratic (b). Each dot is a symbol and represents a point on the
complexplane.
where
a n ∈ C
are the symbols sent andf c
is the carrier frequency. Themodulated signal
s(t)
isa signalwithtwicethe bandwidthof its pulsev(t)
,shiftedinfrequency upto
f c
Hz.LikePAM,thesymbolconstellationinQAMcanbechanged bothinsize
andshape. Figure2.6showstwoexamplesof16-QAMsymbolconstellations.
The number (M) in M-QAM species only the size, not the shape of the
constellation, but typically the points areordered so thedistances between
their neighbors are equal. If energy consumption is of concern, the points
can also be ordered in levels where each level have the same distance to
thecenter of the constellation, see Figure2.6(b). The average energy for a
constellation is calculated bytaking themean squaresum of theEuclidean
distances ofthe pointsintheconstellation:
E av = 1 M
M
X
m=1
kpoint m k 2 ,
(2.8)whichis ageneralization of eq. (2.5).
Because QAMis built oftwo PAM signalsit inherits thecharacteristics
and restrictions of PAM and the choice of pulse follows the same criteria
as discussed later in this chapter. However, there are dierences between
the two modulation schemes. One dierence is that QAM can only trans-
mit symbols at
BW
Baud, compared to the2BW
Baud in PAM. This iscompensated by the possibility to send complex symbols; the eective bit
throughput isthe same.
Another dierence from PAMis theeect ofnot sampling thesignalat
(a) (b)
Figure2.7: Two examplesof distorted 16-QAM constellations. The rstconstellation
(a)hasbeendistortedonlybyadditivewhiteGaussiannoise,thesecond(b)
isaAWGNdistortedreceivedconstellationwhensampling15%outofphase
withrespecttothecarriersignals.
willbearotationofthereceivedsymbolconstellation,whichwilldisturbthe
decoderand can make it decode thesymbols wrong. Figure 2.7 shows two
AWGNdistorted symbolconstellations;one correctlysampled andone that
is sampled too late. The phenomenon occurs because the two carriers get
mixedtogether whensampling at time
t
when2πf c t 6= nπ/2
,wheren ∈ Z
.Tosolvethisproblem,theQAMdetectorneedsaphaselockloop(PLL)that
follows thecarrier signalsand synchronizesthesampler withthecarriers.
2.3 Pulses, Eye Diagrams and Matched Filters
Until now, onlyageneral descriptionofhowacommunicationsystemworks
andtwotypesofmodulationshasbeendiscussed. Noinformationabouthow
tochoosethe pulse,theperformance ofdierent pulsesor how thematched
lterworkshasbeen given. Thissectionwillhopefullygivesome insightson
thesetopics.
2.3.1 Pulse Properties
Thesinc pulse,
sinc
(t) = sin(πt/T s ) πt/T s
,
(2.9)isa socalled overlapping pulse and it isextremely bandwidthecient; but
seeFigure2.3(a). Overlappingpulseshave larger timespread than thenon-
overlappingones,which makesthem interferewithother pulses. Inthecase
ofthe sincpulse, itwill interferewithall other pulsesinthefuture andthe
past. This property makes a true sinc pulse impossible to implement, only
adequateapproximations can be made.
Animportant propertyofthesincpulseisthatitdoesnot interferewith
theother pulseswhenitcrossesthex-axis,whichisevery
T s
seconds;whereT s
, assaid before, is the time between two pulses. The classof pulses thathasthis propertyfollowsa criterion calledthe Nyquist pulse criterion [9].
Denition 2.3.1 A pulse
v(t)
satises the Nyquist pulse criterion ifv(t) = 0
, wheret = nT s
andn = ±1, ±2, ...,
but not att = 0
.Even though the sinc pulse obeys the Nyquist criterion, it can cause
problems when a sampler does not sample a signal at exactly
t = nT s
, i.e.thetopof apulse. AsseeninFigure2.8(a),ifthesymbolat
4T s
issampledat
4.4T s
it willbe decodedto the digital digit zeroinsteadof one.The otherpulse mentioned, theraised-cosine pulse (rc-pulse)[16 ]:
rc-pulse
(t) = sin(πt/T s ) πt/T s
cos(απt/T s )
1 − 4α 2 t 2 /T s 2 ,
(2.10)has a property to mitigate the symptoms of the intersymbol interference
problem. It hasan excess bandwidth factor
α
, which can be chosen intheinterval
[0, 1]
. The larger the excess bandwidth is, the shorter the timespreadof the pulsebecomes. Figure2.3(b) showshowtherc-pulse becomes
narrower when the excess bandwidthis increased. Figure2.8(a) shows how
apulse withno excessbandwidthinterferewiththe otherpulsesandaects
thewholepulsetrain,(b)showshowtheexcessbandwidthfactorcanreduce
thatproblembynarrowing the pulse.
One might think thattherc-pulseisa goodpulse tousebecauseit does
nothavethe sameISIproblemasthesincpulse itis, butonlyifusedwith
an ideal channel with no distortions. If the signal is transmitted through
a non-ideal channel we have to apply a matched lter, which will remove
the zero crossing property of the rc-pulse and introduce ISI. The reason is
that it can not keep the property when it is convolved with itself, and the
matched lter ofanysymmetrical pulse is the pulse itself. Thisis shownin
thesectionabout matched lters, section 2.3.3.
To solve this problem, we can use a variant of the rc-pulse called root
raised-cosine pulse (rrc-pulse) [16 ]. The rrc-pulse is an orthogonal 6
pulse
which,unliketherrc-pulse,doesnotfullltheNyquistcriterion. Thebenet
of thepulse is thatwhen itis convolved withitself, theresult isa rc-pulse.
This means that if a rrc-pulse train is ltered with its matched lter, the
resultingsignalwillbearc-pulsetrain. AccordingtoAnderson[9],itisthese
6
Anorthogonal pulseisuncorrelatedwithitselfshiftedbyanyintegermultipleof
T s
.−4Ts −2Ts 0 2Ts 4Ts 6Ts 8Ts 10Ts 12Ts
−1 0 1 2
time (s) (a)
−4Ts −2Ts 0 2Ts 4Ts 6Ts 8Ts 10Ts 12Ts
−1 0 1 2
time (s) (b)
Figure2.8: Raised-cosinepulsetrainwith0%(a)and100%(b)excessbandwidth. The
signal (solid line)is the sumofthe pulses (dottedlines). Note howmuch
larger thepeaks arewhennoexcessbandwidthis usedcomparedto when
100%isused.Thepeaksarecreatedbytheinterferenceofotherpulses.
−0.5Ts 0 0.5Ts
−2 0 2
Time (s) (a)
−0.5Ts 0 0.5Ts
−2 0 2
Time (s) (b)
−0.5Ts 0 0.5Ts
−2 0 2
Time (s) (c)
Figure2.9: Eye diagramof rc-pulseswith excessbandwidthfactor
α
=0% (a),α
=50%(b)and
α
=100%(c).propertiesthatmakestherrc-pulsethe mostcommonlyusedpulseindigital
communicationsystems.
2.3.2 Eye Diagrams
The most common way to visualize the eect of a pulse shape in the time
domainisthroughan eyediagram. Theeyediagramisa plotof datapoints
repetitively sampled from a pseudo-random bit sequence and displayed by
anoscilloscope orinthis casesimulated inMATLAB, seeFigure2.9. What
is important in the eye diagramis the openinginthe center, also knownas
theeye. Theeye shows how much thepulses overlap eachother and where
itissafetosamplethepulse. Theheight oftheeyedeterminesifthesystem
will be sensitive to noise or not. The lower height, the more sensitive to
noise. Thewidthoftheeyedeterminesitssensitivitytotimingerrorsdueto
theprobabilityofdetectingthewrongsymbol. Figure2.9showstheeectof
theISI, withoutnoise,for theraisedcosine pulse withanexcess bandwidth
of0%, 50%and 100%.
2.3.3 Matched Filters
The matched lter is a lter that has been proven to maximize the output
signal-to-noise ratio (
SN R 0
). The lter itself is a time reversed copy ofthepulse usedto modulate the signalbeforethe transmission.
SN R 0
is bydenition
SN R 0 = y s 2 (t)
E[y n 2 (t)] ,
(2.11)where
y s (t)
is the transmitted signalltered by thematched lterh(t)
andy n (t)
is the lterednoise.y s (t) = Z t
0 s(t − τ)h(τ) dτ, y n (t) = Z t
0 n(t − τ)h(τ) dτ.
(2.12)Theorem 1 The matched lter maximizes the signal-noise ratio of the l-
tered signal (
SN R 0
)and has an impulse response that is a scaled andtimereversed version of the pulse used to modulate the signal.
Proof: We begin the proof by dening the transmitted signal to one
single pulse,
s(t) = v(t)
. Then we simplify the denominator of eq. (2.11) andgetE[y 2 n (t)] = E
Z t
0 n(t − α)h(α) dα Z t
0 n(t − β)h(β) dβ
(2.13)
= Z t
0
Z t 0
E[n(t − α)n(t − β)]h(α)h(β) dα dβ
= N 0
2 Z t
0
Z t
0 δ(t − α − (t − β))h(α)h(β) dα dβ
= N 0
2 Z t
0
h 2 (τ ) dτ,
where
N 0 /2 = σ n 2
is thenoisevariance.To simplify the numerator of eq. (2.11),
y 2 s (t)
, we can use theCauchy-Schwartz inequalitywhich statesthat
Z ∞
−∞
f 1 (t)f 2 (t) dt
2
≤ Z ∞
−∞
f 1 2 (t) dt Z ∞
−∞
f 2 2 (t) dt,
(2.14)whereleftside ofthe inequalityequalstheright sidei
f 1 (t) = C · f 2 (t)
,foranyarbitraryconstant
C ∈ R
. Thesimplicationofy s 2 (t)
becomesy s 2 (t) =
Z t 0
s(t − τ)h(τ) dτ
2
≤ Z t
0
s 2 (t − τ) dτ Z t
0
h 2 (τ ) dτ.
(2.15)Inserting the simplied versions of
y s 2 (t)
andE[y n 2 (t)]
into eq. (2.11) andusingthe Cauchy-Schwartz inequalitygives
SN R 0 =
R t
0 s(t − τ)h(τ) dτ
2
N 0
2
R t
0 h 2 (τ ) dτ ≤ 2 N 0
Z t 0
s 2 (τ ) dτ,
(2.16)where the right part of the inequality is themaximum
SN R 0
possible anditis only obtained if thelter
h(t)
is a scaled and time reversed versionofthepulse
v(t)
inthesignals(t)
. Thereforethematched ltermaximizestheSN R 0
. TheSN R 0
for a pulsev(t)
,can nowbe calculated as:SN R 0 = 2 N 0
Z t 0
v 2 (τ ) dτ.
(2.17)Gaussian LPF FM modulator NRZ base-
band signal
GMSK signal
Figure2.10: GMSKmodulationscheme. TheNRZpulsetrainentersthesystem from
theleft,becomeslteredbyaGaussianlow-passlterandtransmittedby
theFMtransmitter. TheresultingsignalisGMSKmodulated.
2.4 Gaussian Minimum Shift Keying
Gaussian minimum shift keying (GMSK) [3] isanother type of modulation
than PAM and QAM, it isa frequency modulating technique not an am-
plitude modulating that is a well tested and reliable; it hasbeen used in
the GSM cellphone networks for over 15 years. When the old analog cell-
phone networks were to be replaced by a digitalone, GMSK was chosento
be the modulation used. This was because it is possible to use the exist-
inginfrastructureofFMtransmittersto partlycodeanddecode thesignals.
Frequencymodulationisalsoanenergyecientmodulation that,becauseof
itsconstant envelope,can be ampliedwithout distortionbyhigheciency
classCampliers,whichmakesthemodulationwellsuitedforbatterydriven
applicationssuchascellular phones. Thepossibilityto usetheexistingFM
transmitterstocreate aGMSKsignalisalsoofgreatbenetforthis project
when theAdelareceiverhas abuilt-in FMreceiver circuit andthe newspa-
pers aredistributedvia anordinary FMradio channel.
AGMSK signalcan becreated byapplyingaGaussian low-passlterto
a NRZ pulse train and feed a FM transmitter with theltered pulse train.
Figure2.10showsanexampleofhowtoimplementaGMSKtransmitterand
themathematical expression of theGaussian low-pass lter usedinGMSK
is:
h(t) = 1
√ 2πσT s exp
−t 2 2σ 2 T s 2
,
(2.18)where
σ = pln(2)
2πBT s
(2.19)and
BT s
is the bandwidth-timeproduct.If we take the NRZ pulse rect
(t/T s )
and lter it through the lterh(t)
we getthenewpulse
v(t) = 1 2T s
Q
2πBT s t − T 2 s
pln(2)
− Q
2πBT s
t + T 2 s pln(2)
,
(2.20)where
Q(t) = 1
√ 2π Z ∞
t
e − τ
2
2 dτ .
(2.21)Thisnewpulse,showninFigure2.11,canbeusedwithPAMtogenerate
thesamelteredNRZpulsetrainasGMSKdoes. Thismeansthatwefound
−5 −4 −3 −2 −1 0 1 2 3 4 5 0
0.1 0.2 0.3 0.4 0.5
←−−−−−−−BTs=0.1
←−−−−−−−BTs=0.2
←−−−−−−−BTs=0.3
←−−−−−−−BTs=2.0
t/Ts
Ts ⋅ v(t)
Figure 2.11: FourGMSKpulseswithbandwidthparameter
BT s = 0 .1, 0.2, 0.3, 2
.The bandwidth-time product
BT s
aects the time duration and shapeofthe pulse. If
BT s
isa small value, the pulse will be widely spread inthetimedomain and therewill be alot ofISI.Tomitigate theeectsof ISI,an
adaptive lter can be used. The pulse used in the GSM cellphone system
hasavalueof
BT s = 0.3
and anadaptive lteris used.FormoreinformationaboutGMSKanditsimplementationdetails,Laster
[14 ],Chongburee[11 ] and [3]arerecommended.
2.5 Spectrum Analysis
ToseehowtheFMsystemaects thespectrumof thetransmitted signal,a
lab-test wasdone usinga FMmodulator. Thereceived signalinthis test is
notasdistortedasasignalofareal-worldtest,becausethedistortionsinthe
lab environment are not assevere as in reality. However, it will give some
insight ofhow the combination of aFMtransmitter andreceiveraectsthe
signal.
Before transmission, the FM modulator removes the frequency compo-
nents below 30Hz and amplies the high frequencies. To compensate for
the amplication, the receiver lowers the amplitude of the high frequencies
when demodulating the signal. This is done to get a higher SNR at the
high frequencies and it should, in theory, result in the transmitted signal
but often the resulting signal is either amplied or dampened at the high
frequencies,aswill be shownlater. Unfortunatelyit notpossible toretrieve
the frequenciesbelow30 Hz.
The test was done by constructing a white noise signal in MATLAB,
whichwastransmittedthroughtheFMmodulatorandrecordedbytheAdela
receiver. Thereafter it was taken into MATLAB where its power spectral
0 5 10 15 20
−115
−110
−105
−100
−95
−90
−85
−80
−75
−70
−65
Frequency (kHz)
Power/frequency (dB/Hz)
Figure2.12: Powerspectraldensityestimate,viaWelch,ofawhite noisesignaltrans-
mittedthroughaFMmodulatorandrecordedontheAdelareceiver. Notice
thenegativespikebetween0-30Hz,itgoesdownto-111dB.Thedipon19
kHzistheresultofasocalledpilottoneintheFMsystem.
of spectral estimation [8]. The spectrum of the received signal is shown in
Figure2.12. Noticetheeect ofthe30 Hz high-pass ltering.
Lookingatthepowerspectraldensityplot,itisclearthatitisnotpossible
tosendsignalswithfrequencycontentabove18.5kHz,becauseofthedipat
19 kHz and according to Wikipedia[6], the FMsystem is specied to only
transmit signalsupto 15kHz. Thedipisthe resultofa socalledpilot tone
intheFMsystem. For informationabout theFMsystemand itspilot tone,
seeLarsson[13].
One can also see a small dampening of the frequencies above 5 kHz.
Thiscanbecorrectedusinganequalizer,but thelowfrequenciescan notbe
restored, which can be a problem for baseband modulations such as PAM
andGMSK.
2.6 Discussion and Conclusion
Nowwehavediscussedthreemodulationtechniques,dierentpulsesandseen
theeectofthemodulation/demodulationintheFMsystem,butwhatmod-
ulationshouldbeusedinAdela? Inthis sectionthebenets anddrawbacks
of the investigated modulations will be discussed and nally a conclusion
2.6.1 Reasons for Using PAM
Pulseamplitude modulation wastestedbecauseof itssimplicityandeaseof
implementationonalimitedhardwareplatform. Itwasagoodstartingpoint
whenexperimentingwithtransmissions. Itsperformanceisgoodinbaseband
channels andthequalitiesmentionedbeforemakesitagoodcandidate. The
modulationhasalsobeenusedfordatatransmissionsoverFMbefore,inthe
ERMES[10 ]pagingsystem. TheERMESsystemusesa4-PAM modulation
to achieve a symbolrate of3125 Baudina FMchannel using 25kHz [4 ].
The drawbacks with using PAM lies inthe FMsystem. The FMtrans-
mittershasahigh-passlterthatremovesthelowerfrequenciesbelow30Hz,
aswas shown before. This can be avoided ifthe bandwidth
BW
is halvedand the signalis modulatinga carrier above the halved
BW
or by using aPAM-like carrier modulation like Carrier-less Amplitude/Phase modulation
(CAP) [2]. Unfortunately, there was not enough time to investigate CAP
further.
2.6.2 Reasons for Using QAM
TheQAMmodulationwastestedbecauseithasaverybroadrangeofdevices
thathavebeenusingitforalongtime;itisareliablyandprovenmodulation.
Computermodemsusesittoremovetheeectsofapossiblebias-levelinthe
telephone system and because the FM system has a high-pass lter which
removes the frequencies below 30 Hz, QAM is a candidate modulation for
Adela.
ThedrawbacksofQAMarethecomplexityandtheneedofacarriersyn-
chronization loop. Thesynchronization can bedone using eithera software
PLLor a modiedsymbolsynchronizer.
2.6.3 Reasons for Using GMSK
Thestrongest reason for using GMSK is thesimplicity and the factthat it
hasbeen usedwithsuccess for over 15 years intheGSM cellphonesystem.
The dierencesbetween PAM via FM and GMSK are not signicant, both
modulationsareconstructed prettymuchthesame way. Itisonly thepulse
thatdiers,but PAM is easierto decode iftherrc-pulse isused, due to the
lesserISI. Therefore itisquestionable to useGMSK insteadofPAM.
2.6.4 Conclusion
The similarities between GMSK and PAM sent through a FM channel are
considerable,aGMSKsignalcanbebuiltusingaPAM signal. Itisonlythe
pulse thatdiers, but GMSK hasthe drawback of more ISIand it requires
a better equalizer and detector. Therefore the PAM modulation scheme is
−1.5 0 −1 −0.5 0 0.5 1 1.5 1
2 3 4 5 x 10 5
Sample value (a)
NR of samples
−1.5 0 −1 −0.5 0 0.5 1 1.5
2 4 6 8 10 12 x 10 4
Sample value (b)
NR of samples
Figure2.13: Histogramoftherawsamplesfroma23kBaud/s2-PAMsignalmodulated
byarrc-pulse with 30%excessbandwidth. Thesignal issampled at the
optimumsamplingpoint. (a)undistortedsignal. (b)lteredusinga30Hz
high-passlter.
The QAM modulation is a more sophisticated modulation than PAM,
it has the nice property that it will not be aected by the removal of the
lowfrequenciesintheFMsystem,but thebenetsofQAMdonot outweigh
itscomplexity comparedto PAM.ThehighfrequencydistortionsintheFM
systemarefargreaterthantheremovedlowfrequencies,thusitisabetteruse
of time to implement an equalizer than using a more complex modulation
that is not aected by the 30 Hz high-pass ltering. Therefore the PAM
modulationscheme waschosento beimplemented ontheAdelareceiver.
To see how much the low frequency ltering would aect a PAM sig-
nal, a test was performed in MATLAB, see Figure 2.13. The samples in
the histogram were sampled at the optimum sampling point. Notice how
muchwiderthe spikesbecomeswhentheltering isapplied. Itisclear that
the high-pass lter aects the performance of the whole system negative;
but it is still possible, in theory, to transmit a 8-PAM signal. That would
make it possible to send high quality audio, or multiple newspapers inone
69 kbit/23kBaud channel.
Demodulation
Todecode ananalogsignaltoadigitalbitstreamthesystemhastodemod-
ulatethesignal. To dothis,at leastthree operations have to be performed.
The rst, in a fully digital receiver system, is to sample and lter the re-
ceivedsignalwiththe matched lter,seeFigure3.1. Afterthat,thereceiver
hastolockonto thesymbolstream;nd therightphaseand pickasymbol-
sample 1
. Thethirdthingneededisasymboldetectorwhichdecodesasample
andmapsittoasymbol. Thesearetheminimumrequiredoperations,under
ideal circumstances. Under non-ideal circumstances an equalizer isneeded.
Itisanextremelyimportantpartinmostreal-worldcommunicationsystems
andits purposebeingto mitigatetheeects ofthechanneldistortions.
This chapter will discuss and explain one technique for each of these
three steps in the decoding process. First a symbol synchronization algo-
rithmcalleddecisiondirectedmaximumlikelihood (DDML)willbediscussed,
thereafter a symbol detector called maximum a posteriori (MAP) detector
andnally anequalizeralgorithm calledleast mean square (LMS)equalizer
arediscussed.
3.1 Symbol Synchronization
Symbolsynchronization isoneofthemostimportant partsofadigital com-
munication system. Without a synchronizer it is impossible to decode a
received signal. The taskof the symbolsynchronizer is to, with knowledge
1
Thesymbol-sampleisthesamplethatischosentobedecodedtoasymbol.
Matched filter Equalizer Synchronizer Detector
nT s
Sampler
of the symbol rate, actively calculate and correct the symbol phase. To
actively correctthephaseis important because theoscillatorson thetrans-
mittingandreceivingsystemsmightdriftintime,withrespecttoeachother;
i.e. it can never be guaranteed that they have exactly the same frequency
andphase.
The phase aects the error probability of the decoder, even if the re-
ceiversamplesthesymbolsatthesame symbolfrequencyasthetransmitter
is sending them. If a system samples, for example, Figure 2.8(b) at time
t = nT s + φ
, wheren ∈ Z
and the phaseφ = 0.4T s
; even very little noisecan lead to detection errors. Thus the task of the symbol synchronizer is
to adjust the phase to make the system sample the signal at the optimal
samplingpoint thus improving the chances ofdecoding thecorrectsymbol.
In this section a symbol synchronizer calleddecision directed maximum
likelihood (DDML) [16 ] synchronizer is discussed. Decision directed means
thatthealgorithm takesthe detectedsymbolintoconsiderationwhentrack-
ingthesignal. Itwaschosenafteraliteraturestudyofthreesynchronization
algorithmsthe DDML, non-decisiondirected maximum likelihood [16]and
early-late gate [9] synchronization algorithms because it is relatively easy
to implement and it givesa betterresult locking onto thesymbols than the
otherinvestigatedtechniques. Itisversatile,andsuitableforbasebandPAM
signalsbutitcan alsobemodiedto workwithcarriermodulations suchas
QAM.
Sampler
VCO d
dt
å d
dt y[n+ φ ]
N
a n
n+ φ y[n]
φ [n]
Figure3.2: Decisiondirectedmaximum-likelihoodsynchronizer.
Briey described one can say that theDDML synchronizer consist of a
dierentiator, a VCO 2
controlled sampler and a sliding window averaging
lter, seeFigure 3.2. It uses thereceived signal afterthe oversamplingand
the matched lter, which works as a correlator. The resulting correlation
signal,
y[n]
inFigure3.2,isusedforbothsymbolsynchronizationandsymbol detection. The symbol synchronizer uses the correlation signal for ndingthe points on thesignal which give the highestcorrelation, i.e. theoptimal
samplingpoints. Tondthesepoints,thecorrelationsignalisdierentiated;
sampledagain, i.e. the optimal sampling points arechosen, and multiplied
by the detected symbol from the detector. See Figure 3.3 for the eect of
2
−4Ts −2Ts 0 2Ts 4Ts 6Ts 8Ts 10Ts 12Ts
−1.5
−1
−0.5 0 0.5 1 1.5
time (s)
Figure3.3: Pulsetrain(dashedline)afterthematchedlterandtheVCOinputsignal
(solidline)beforetheslidingwindowaveragelter. TheVCOinputsignal
hasbeenampliedtentimesinthisplot.
thisoperation. Ifthe correction signalisnegative,itmeansthatthesystem
is sampling the signaltoo late and the VCO will make the sampler sample
abit earlier. Ifthesignalispositive,theoppositewill happen. Observe the
zero crossings of the correction signal, the signal hasdiscontinuities in the
pointswhere
y[n]
crossesthe time axis.Aftermultiplication,thesignalislteredbyanaveragingslidingwindow
lter,whichresults inavery lowfrequencycontrolsignal, usedbytheVCO
to correct the next sampling point. The ltering is needed to remove the
noise which is amplied by the derivative. Mathematically the correction
signalfor the n:thsample can be expressedwiththefollowing expression:
φ[n] = C N
N
X
i=1
a n−i d
dt y[n − i],
(3.1)wheretheconstant
C
isthegain,N
isthelengthoftheslidingwindowlter,y[n]
is then:th sample fromthe received signal after theltering anda n
isthecorrespondingdetected symbol.
This signal makes it possible for the system to cope with a certain fre-
quencydierence withrespectto the transmitting system, butif thedier-
ence becomes to large, the system will not be able to lock onto the signal
andthedecodingofthesymbolswillbreakdown. However, thisisgenerally
3.2 Symbol Detection
Thetaskof the symboldetectoristo decodea sample tothe symbolwhich
is the most probable. A simple way is to calculate which symbol in the
constellation that hasthe value nearest to the sample; i.e. nd thesymbol
s i
,which minimizes the Euclidean distanced =
mini k r − s i k .
(3.2)This type of detector is called maximum likelihood (ML) [16 ] detector and
isaverypopulardetectorbecause ofits simplicity andgoodperformanceif
the symboldistribution of the transmitted data isunknown or independent
andidentically distributed (IID).
If the data is not IID, this type of detector will give inferior results
and therefore the probability density function of thetransmission symbols
shouldbetakeninto consideration but ifthedistribution isunknown, the
ML detector is the one which provides the bestperformance. Thisis what
moresophisticated detectors such asthemaximum a posteriori (MAP)[16 ]
detector does, but at the price of increased computational complexity. It
is done by nding the symbol
s i
that maximizes the probability of being detected given thatthe sampler
hasbeen received:P (s i |r) = P (s i
sent andr
received)
P (r
received) .
(3.3)This entire expression is not needed to calculate what symbol has the
greatest probability, for example the denominator can be reduced because
itis independent of what symbol is tested inthe numerator. However, the
numerator canalso berewritten as
P (s i
sent andr
received) = P (r
received|s i
sent)P (s i
sent),
(3.4)which in turn can be simplied because the probability that
r
is received,given that
s i
is transmitted, is identical to the probabilitythat the noisen
equalsthedierence between
r
ands i
:P (n = r − s i ) = P (r
received|s i
sent).
(3.5)Thisisbecausethe channelnoiseisassumedto beadditiveandindependent
ofthe signal.
These simplications results in eq. (3.6) where the symbol
s i
whichmaximizestheexpressionisthesymbolthatwasmostprobablytransmitted.
P (n = r − s i )P (s i ).
(3.6)Thefunction
P (n = r−s i )
caneitherbemodeledorcalculatedusingreceivedLMS algorithm Sync & detect
x[n] d[n] d[n]
e[n]
^
- +
Figure3.4: Blockschematicofasystemusingtheleastmeansquarealgorithm.
Thistypeofdetector, whichtakestheobservedinformation about
r
andthepriorknowledgeabout
s i
into considerationwhen makingthedecision a posteriori that is, after the observation is called maximum a posterioridetector. TheinterestedreaderisreferredtoAnderson[9 ]forfurtherreading.
3.3 Adaptive Equalization
An equalizerisa necessarypartof the decoderprocess. Itstaskisto elimi-
natechanneldistortionandminimizeISI. Withouttheequalizeritisalmost
impossible to decode data with satisfying results under non-ideal circum-
stances.
In this section some theory about how to construct a minimum mean
square error equalizer is discussed, a short explanation of why we can not
usethis inreal-timeand howto makea suitablesolution.
Thereareseveralwaystoconstructanequalizer;oneisto,duringthede-
signphaseofthecommunicationsystem,constructanequalizerfor aknown
channel. Thistype of predetermined equalizeronly workson theparticular
channelit was constructed for and ifthe channel varieswithtime, theper-
formance of the equalizer will degrade. This is not a good solution. For a
digital communication systeman equalizer thatdoes not know thechannel
inadvanceandone thatiscapableofadapting toa timeinvariant channel's
varyingchannelresponseisneeded. Tosolvethisproblemanadaptiveequal-
izercanbedesigned usingtheleastmean square (LMS)[12]algorithm. This
algorithm which is probably the most commonlyused adaptive equalizer
algorithmcanbeusedtondtheltercoecientvector
w
,inaFIRlter, whichminimizes themean squareξ n = Ee 2 n ,
(3.7)of the error signal
e n
of a transmitted signal that is wide sense stationary (WSS) and distorted by additive white Gaussian noise. A block schematicofa systemusingthe LMSalgorithm isshowninFigure3.4.
Tond the meansquareerror, wehave to dene whattheerror is. Lets
dene the error as the dierence between the desired symbol
d n
and theestimatedsymbol
d ˆ n
,e n = d n − ˆ d n ,
(3.8)wherethe desiredsymbol
d ˆ n
isthedot productbetween theltercoecientvector
w
andthe inputsamplevectorx
,d ˆ n = w · x,
(3.9)w = [w 0 w 1 w 2 . . . w m ] T , x = [X n X n−1 X n−2 . . . X n−m ] T .
The elements of the sample vector
x
;X n , X n−1 , . . . , X n−m
; are dened asWSSstochasticvariables.
Tominimizethemeansquareerror
ξ n
,wemustndthevaluesofw
that resultinmakingthegradientofξ n
,withrespecttow
,equalzero,i.e. ndingw
sothat∇ξ n = 2E e n ∇e n = −2E[e n x ] = 0,
(3.10)where
∇e n = ∇(d n − ˆ d n ) = −x.
(3.11)As seen in eq. (3.10), the gradient
∇ξ n
equals zero whenE[e n x ] = 0
.Tosolvethis,wecan rewritetheequationintomatrix notationusingacross
correlationvector anda autocorrelationmatrix as
E[e n x ] = r dx − R xx w = 0,
(3.12)where
r dx
is the cross correlation vector betweend n
andx
.R xx
is the autocorrelationmatrix ofx
.r dx =
E[d n X n ] E[d n X n−1 ] · · · E[d n X n−m ] T
(3.13)
R xx =
E[X n X n ] E[X n X n−1 ] . . . E[X n X n−m ] E[X n−1 X n ] E[X n−1 X n−1 ] . . . E[X n−1 X n−m ]
.
.
.
.
.
.
.
.
.
.
.
.
E[X n−m X n ] E[X n−m X n−1 ] . . . E[X n−m X n−m ]
(3.14)
The lter coecient vector
w
can now be calculated by solving eq. (3.12), i.e. calculate the inverse of the autocorrelation matrixR xx
multiplied byr dx
:w = R −1 xx r dx .
(3.15)Unfortunately this requires information about the symbol distribution
andthedistributionofthereceivedsamples,whichwillnotbevalidifsome-
thingchangesinsidethechannel. Thiscanbesolved byapproximating
R xx
and
r dx
inreal-time by calculating these using previous samples, inverting the matrix and doing the matrix-vector multiplication. This is a proces-sor intensive process and is rarely, if ever, used inpractice. However, it is
possible to iteratively calculate thelter coecients
w
usingthemethodofThe basic ideaof the steepestdecent method isasfollows. Let
w n
be a vector that minimizes the mean square errorξ n
at timen
. At timen + 1
,w n
will not be optimal any more and we have to calculatew n+1
bytaking astepofsizeµ
downthequadraticerror surfacetogetclosertotheoptimalsolution. This is done by subtracting the gradient of the error, at time
n
,multipliedbyastep size
µ
:w n+1 = w n − µ∇ξ,
(3.16)where
µ
is limitedbyλ max
,themaximum eigenvalueof theautocorrelation matrixR xx
:µ < 1 λ max
.
(3.17)For information on how to calculate
λ max
,seeHayes[12 ].But to calculate
∇ξ
, we still need some statistical information aboute n
andx
, otherwise we can not calculateE[e n x ]
. Fortunately, the LMS algorithm will converge even if we do not have that information. We canapproximate
E[e n ]
withe n
andE[x]
withx
, i.e.E[e n x ] ≈ e n x
. The new updated equationforw
is now:w n+1 = w n + 2µe n x ,
(3.18)Ifthereceivedsignalandthetransmittedsymbolsarejointly wide sense
stationary processes,which is assumed, theLMS equalizer will converge to
an optimal solution. Figure3.5 and 3.6shows the eect of theequalizer on
a2-PAM signalthat wastransmitted througha FMchannelwhen theFM-
modulator wascongured to useanerroneous preemphasis 3
setting. Notice
howmuch bettertheconditions arefor symboldetection aftertheequaliza-
tion. Onecannotethattheamplitudeofthebasebandsignaldirectlyaects
theresult of the equalized signal. If thetransmitted baseband signalhas a
low amplitude, then the samples in Figure 3.5(a) will be close to zero and
theequalized outputwill bemore wide spread.
For further reading about adaptive ltering, the book Statistical digital
signalprocessing andmodeling byMonsonH.Hayes[12] is recommended.
3
Thepreemphasis settingis a parameterused onthe FM-modulatorto control how
muchthe higherfrequencies are amplied beforetransmission. If the receiver doesnot
−0.4 0 −0.3 −0.2 −0.1 0 0.1 0.2 0.3 0.4 1000
2000 3000 4000 5000
Sample value (a)
NR of samples
−2 −1.5 −1 −0.5 0 0.5 1 1.5 2
0 2000 4000 6000 8000 10000 12000
Sample value (b)
NR of samples
Figure3.5: Histogramofa2-PAMsignal,modulatedusinga30%excessbandwidthrrc-
pulse. Thesignal was transmittedthroughaFMmodulatorand recorded
inthe Adela receiver. (a)shows the rawsamples. (b)shows the samples
afterequalization. TheequalizedhistogramhastwoGaussianshapedparts
partlybecauseofthe30Hzhigh-passlteringintheFMsystem. Thelength
oftheequalizerwas33symbolsand
µ = 0.25
.−0.5 0 0.5
−0.3
−0.2
−0.1 0 0.1 0.2 0.3
Time (s) (a)
−0.5 0 0.5
−2
−1.5
−1
−0.5 0 0.5 1 1.5 2
Time (s) (b)
Figure3.6: Eye diagramofthe signal inFigure 3.5. Thediagramhas beencalculated
usingthesampledsignal. Thereforeitisnoisierthaninrealitybecauseofthe
errorsthesymbolsynchronizermakes. Theleftgure(a)istheeyediagram
beforeequalizationandtherightdiagram(b)isafterequalization.